Magnetron amplifiers



Dec. 6, 1960 E. c. DENCH MAGNETRON AMPLIFIERS Original Filed Jan. 24, 1952 2 Sheets-Sheet 1 A TERA/E) 5 014 420 Z 52: Zc 5 i 1 l rk MAGNETRON AMPLIFIERS Edward C. Dench, Needham, Mass, assignor to Raytheon Company, a corporation of Delaware Original application Jan. 24, 1952, Ser; No. 268,097, now Patent No. 2,850,671, dated Sept. 2, 1958. Di vided and this application June 5, 1958, Ser. No.

6 Claims. (Cl. 315-393) This application is a division of my application Serial No. 268,097, filed January 24, 1952, which matured into Patent 2,850,671 on September 2, 1958.

This invention relates to electron discharge devices, and more particularly to devices of the magnetron amplifier type.

It has been found that magnetron amplifiers previously constructed had an undesirable tendency to oscillate when a sufiicient voltage was applied to the device in the presence of a particular magnetic field to create conditions whereat amplification was possible. While the oscillations may be damped out by loading down the signal wave transmission structure, which makes up the anode, such loading also absorbs power from the amplified signal, hence reducing the efliciency and amplification factor of the device.

One source of oscillations is the operation. of the discharge device under conditions whereat electrons move along paths adjacent the signal wave transmission net- Work in the anode at velocities sufficient to produce 1r mode oscillations. The 11' mode oscillations encountered are similar to those generated in a conventional magnetron oscillator and are produced when adjacent anode members making up the signal wave transmission structure differ in phase by substantially 1r radians. These oscillations are the result of feedback within the signal wave transmission network, substantially independent of the terminations at the ends thereof, with each pair of adjacent anode members together with the space therebetween behaving as a substantially resonant cavity. Therefore, such oscillations cannot be satisfactorily eliminated by adjustment of the impedance match at the signal input and output connections to the signal wave transmission network. Moreover, increasing the velocity of the electron stream substantially above the required velocity for oscillation at the 11' mode frequency will not always eliminate this source of oscillations since the transmission line at the rr mode has an extremely high Q, and hence is coupled strongly enough to the electron stream to interact therewith sufficiently well to produce oscillations possibly by slowing down some of the electrons in the stream to velocities where more efiicient interaction at the 1r mode frequency occurs.

This invention discloses a magnetron amplifier wherein the device may be operated in a region where amplification is possible but where oscillation at the Jr mode frequency is not probable. Briefly, this is accomplished by using in the anode structure a signal wave transmission network having a lower cutoff frequency, said anode structure being such that the phase velocity of a component of a signal traveling along said network at frequencies other than said cutoff frequency is different than the phase velocity of said component at said cutoff frequency. The term lower cutofi frequency, as used throughout the specification and claims, is hereby defined as that frequency below which the desired component of the signal will not propagate along the trans-.

mission network and above which said component will propagate along said network.

Specifically, in the embodiment illustrated herein where a strapped anode structure is used, it has been found that u should be greater than .67 where on is a normalized design parameter determined from the formula where w =the lower cutoff frequency,

L =the strap inductance encountered in one section or cavity of the anode structure, and

Z ='the characteristic impedance of the cavity.

The reasons for the eifect of the design parameter a on the ability of the transmission network to oscillate in the 1r mode will be demonstrated in greater detail. presently.

This invention further discloses a novel method of coupling the input and output devices to the signal wave transmission network. Briefly, the coupling is accomplished by connecting the outer conductor of a coaxial line to the end anode member of the signal wave transmission network at a point adjacent the inner end of the anode member and substantially half way between the sets of straps. The central conductor of the coaxial line extends through an aperture in the end anode member spaced therefrom and is connected to the anode member adjacent the end anode member. Such a coupling device sees the signal wave transmission network substantially as a series of cascaded 11- section filters.

For the particular range of values of the design parameter 0: previously discussed, it has been found that the characteristic impedance of a transmission network analyzed as cascaded 1r section filters remains substantially constant over a Wider range of frequencies than the same transmission network analyzed as a series of cascaded T-section filters. Hence, an output coupling device which sees substantially 1r section filters in the transmission network may couple a constant impedance load to the transmission network with a better degree of match over a wider range of frequencies than can a coupling device, such as a connection to the straps, which sees sub stantially T sections in the transmission network.

Other and further objects and advantages of this invention will be apparent as the description thereof progresses, reference being had to the accompanying drawings wherein:

Fig. 1 illustrates a longitudinal cross-sectional view or" an electron discharge device embodying this invention;

Fig. 2 illustrates a transverse cross-sectional view of the device shown in Fig. 1 taken along line 2-2 in Fig. 1;

Fig. 3 illustrates a partially broken away isometric view of the device shown in Fig. 1, illustrating the details of the input or output coupling devices;

Fig. 4 illustrates a partially broken away isometric view illustrating a further embodiment of an input or output coupling device which may be used in the device illustrated in Fig. 1;

Fig. 5 illustrates a graph showing the relationship between frequency and phase velocity of a component of a wave travelling in the signal wave transmission network used in the device of Fig. l for various values of the design parameter a; and

Fig. 6 illustrates a graph showing the relationship between the characteristic impedance of the signal wave transmission network used in the device shown in Fig. l, and frequency for various values of the design parameter 0: when said transmission network is analyzed as a series of cascaded 11' section filters and when said transmission network is analyzed as a series of cascaded T-section filters.

Referring now to Figs. 1, 2, 3 and 4, there is shown an electron discharge device comprising anode structure which is fabricated to form a signal wave transmission network. Anode structure Ill-comprises a backing support member 11 which is shown as a flat plate of conductive material, such as copper. Extending downwardly from plate 11 is a plurality of anode members 12 which are shown'here, for example, as substantially rectangular planar members. Anode members 12 are rigidly attached at their upper ends to support member 11 and are alternately connected at points on their edges adjacent their lower ends by conductive straps 13 according tovwellknown practice. Planar members 12 are positioned substantially perpendicular to support member 11 and. to the conductive straps 13.

The anode members 12 are positioned within a conductive evacuated envelope of which the support member 11 is a part. The envelope comprises side walls 14 attached to support member 11 and a lower Wall 15, sealed to side members 14, and end walls 16 sealed to the ends of the box-like structure made up of members 11, 14, and 15.

Positioned inside the envelope adjacent the lower ends of anode members 12 is a metallic trough-like member 17, the bottom of said trough-like member being positioned parallel to the lower edges of anode members 12 and the sides 18 of trough-like member 17 extending upwardly to a point slightly above but spaced from the lower corners of anode members 12. Trough 17 is supported by means of insulated supports 19 which provide electrical connection of trough 17 with circuits outside the envelope but which prevent electrical contact of trough 17 with the envelope or the anode structure 10. Trough 17 and the insulated supports therefor are described in greater detail in my copending application Serial No. 255,499, filed November 8, 1951, now Patent No. 2,809,- 328, dated October 8, 1957.

A cathode structure 20 is positioned adjacent one end of the signal wave transmission network made up of anode members 12 while a catcher electrode 21 is posi tioned adjacent the other end of said signal wave transmission network. The purpose of the cathode 20 is to emit electrons which, under the influence of the proper electrostatic and magnetic fields produced in the space between trough 17 and the lower ends of the anode members 12, will move along paths adjacent the anode members 12 and, after amplifying any signal present in the network through interaction therewith, the electrons will impinge on the catcher electrode 21. The particular details of the cathode 20 and catcher electrode 21, as Well as. the support and electrical connections thereto, are described in greater detail in the aforesaid copending application. The magnetic field may be produced by means of a magnet which is connected to magnetic pole pieces 22, positioned adjacent the external sides of side members 14. g Y

The anode members 12 do not extend all the way to the end members 16 but a space is left adjacent the end members 16 where the members 12 have been omitted. Signal coupling devices 23 are connected at each end to the signal wave transmission network made up of the anode members 12. The coupling device 23 comprises a coaxial line having an outer conductor 24 sealed through end plate 16 and terminating in the end anode member 12 at a point substantially half way between the sets of straps 13 and adjacent the lower end of said anode member. Positioned inside conductor 24 and spaced therefrom is a central conductor 25 which extends through an aperture in the end anode member 12 spaced therefrom and is connected to the anode member adjacent the end anode member. Inner and outer conductors 24 and 25, after passing outwardly through end plate 16, have a tapered transition section 26 designed to match the im- 4 pedance of the device being coupled to the signal wave transmission network to the impedance of said network. Thereafter, central conductor 26 is insulatedly sealed to the outer conductor 24 by means of an insulating seal, not shown.

Referring now to Fig. 5, there is shown a graph illustrating the relationship between frequency and the phase velocity of a component of a wave traveling along the signal wave transmission network for various values of the design parameter a. This relationship may be calculated from a formula derived as follows: The signal wave transmission network is analyzed as a series of T-section filters, one such section comprising the cavity 7 formed by two parallel anode members 12 and the portions of the straps included therebetween. Such T sections are shown in copending application Serial No. 66,249, filed December 20, 1948, by William C. Brown. One half of the strap inductance is positioned in each of the horizontal arms of the T and has an impedance equal to 'jwL, Where to is any frequency applied to the network. The vertical arm of the T represents the impedance of the cavity connected across the straps, said impedance being given by the formula jZ tan )8! where.

Z =the characteristic impedance of the cavity,

l=the efiective length of the cavity, and )\=the wavelength at said frequency.

' The phase velocity of a component of the wave travelling along the signal wave transmission network is given by the formula wA V- 0 (2) where A=the length of a network section and =phase shift per network section.

At the lower cutoff, 0:0 and V=V,

Thus

and

where w =the cutoff frequency in radians.

0 must now be found in terms of the design parameters. From network theory At lower cutoff 4 X 2 000 1 Thus 6=cos- 1+:- 12

0 tan 2 60c 9 is calculated for values of w/w from 0:0 to 0:11- (i.e. over the pass band) for various values of 0:. Using these values of 0, the values of V/V, are then computed; the results are plotted in the graph illustrated in Fig. 5.

The normalized phase velocity is plotted along the axis of ordinates while the normalized frequency is plotted along the axis of abscissae. Curves are plotted for values for a of 10, 1.5, 1, .67, .25, and .10 and are indicated by curves 27, 28, 29, 30, 31, and 32, respectively. At the 7r mode frequency indicated as a normalized frequency of 1 on the graph, the normalized phase velocity is unity for all of the curves as is indicated by point 33 on the graph. As the frequency is increased, the curves 27 through 32 diverge with all the curves initially extending downwardly from point 33. The curve 27 indicating a design parameter at of continues sharply downward until it reaches a normalized phase velocity of approximately .56 at a normalized frequency of approximately 1.11 as indicated by point 34 on the graph. Curves 28 and 29 level off for a short period at normalized phase velocities of approximately .88 and .92, respectively, over a frequency range extending from the normalized frequency of 1.1 to substantially 1.3 and 1.1 to 1.4, respectively. These curves then again veer downward. Curve 30 after extending downward from point 33, as frequency is increased, levels off and turns upward to again reach a normalized phase velocity of 1 at a normalized frequency of approximately 1.4 after which it again veers downward as frequency is increased. Curves 31 and 32 after extending downwardly from point 33, as frequency is increased, veer upwardly again and exceed the normalized phase velocity of 1 at normalized frequencies in excess of 1.08 and 1.04, respectively, as is indicated by point 35 and point 36, respectively. The curves 31 and 32 extend upwardly to normalized phase velocity maximums of approximately 1.19 and 1.35, respectively, at normalized frequencies of approximately 1.6 and 1.7, respectively. The curves 31 and 32 then veer downwardly and again reach normalized phase velocities of 1 at frequencies of around 1.85 and 1.94, respectively, as indicated by point 37 and point 38, respectively.

Thus, it may be that for values of the design parameter a greater than .67, the transmission network will transmit waves at all frequencies Within the pass band at phase velocities which are less than the phase velocity of the lower cutoff or 11' mode frequency. With such an anode structure, the velocity of the electrons directed past the anode members may be adjusted by adjustment of the anode voltage to a value which is below the phase velocity of the 71' mode. It has been found that under these conditions oscillations will not occur at the 11' mode frequency. If values of a which were less than .67 were used, the voltage required would have to be very close to or above the voltage required to produce electron velocities equal to the phase velocity of a wave at the 1r mode frequency, and under these conditions oscillations at the 11' mode frequency would probably occur if the tube were not highly damped, for example, by the insertion of excessive amounts of lossy material.

In addition, it may be noted that curves 28 and 29 are relatively flat over a wide range of frequencies, for example, between the normalized frequencies of 1.1 and 1.4 or 1.5 and hence the anode voltage may be adjusted to a value which will produce electron velocities at the phase velocities of the waves in the signal wave transmission structure over this range of frequencies where values of on within this range are used, thereby insuring substantially the same degree of interaction between the electron stream and the waves, and hence the same gain for the electron discharge device over this range of frequencies. The curves 36 and 38 which rise above a normalized phase velocity of 1, on the other hand, are not fiat over any substantial portion thereof and hence the gain of an amplifier tube operating on these curves, even if oscillations could be prevented, would vary considerably with frequency.

Referring now to Fig. 6, there is shown a graph illustrating the relationship between the characteristic impedance of the signal wave transmission network and frequency for various values of the normalized design parameter or when the network is analyzed as a series of cascaded T section filters and when the network is analyzed as a series of cascaded 11' section filters. Plotted along the axis of ordinates is the normalized characteristic impedance of the network Z/Z where Z, is a characteristic impedance of the network. Plotted along the axis of abscissae is the normalized frequency The curves illustrating analysis of the signal wave transmission network as a series of cascaded 11- sections are shown in solid lines for values of 12 equal to 10, 1.5, .67, .25 and .1 as are illustrated by curves 39, 40, 41, 42, 43, and 44, respectively.

The curve 39 has a normalized impedance of 50 at a normalized frequency of approximately 1.01 as is indicated by point 45. As frequency is increased, it drops rapidly to a minimum normalized impedance of approximately 22 at a normalized frequency of 1.06 as is indicated by point 46 and thereafter rises rapidly to a normalized characteristic impedance value in excess of 60 at a frequency of approximately 1.11 as is indicated by point 47. The curve 40 has a normalized impedance of 7 at a normalized frequency of 1.05 as is indicated by point 48 and falls gradually to a minimum along a curved line to a normalized impedance of approximately 4 at a normalized frequency in the range between 1.2 and 1.3 as is indicated at point 49 and thereafter rises gradually to a normalized impedance in excess of 10 at a normalized frequency of 1.47 as is indicated by point 50. This curve has a relatively constant normalized impedance, for example, within a difference of 1 over a frequency range from 1.1 to 1.4 and hence would present conditions allowing good input and output matching to the network over this range of frequencies. Reference to curve 28 in Fig. 5 which is for the same value of 0: indicates that this range of frequencies could be used to amplify with electron velocities on the order of percent of the velocity required for 11' mode operation.

Similarly, curves 41 and 42 in Fig. 6 are relatively gradual having normalized characteristic impedances of approximately 4.2 and 3.3, respectively, for a normalized frequency of 1.1 as is indicated by point 51 and point 52, respectively. These curves gradually fall to minimums at normalized impedances on the order of approximately 3 and 2, respectively, at frequencies within the range from 1.2 to 1.4, then rise gradually to normalized impedances in excess of 8 at normalized frequencies of approximately 1.58 and 1.67, respectively, as is indicated by point 53 and point 54, respectively. Since these curves are relatively fiat'over a wide range of frequencies, and reference to Fig. 5 shows that for these values of (x amplification is practical without risking oscillation at the ar mode, design of an electron discharge device and output coupling structure for this range of values of a, namely a=.67 to a=1.5, is feasible. Curves 43 and 44 are also relatively flat over wide ranges but reference to Fig. 5 indicates that for these values of a the required electron velocity is greater, for most of the frequencies, than that necessary for 11' mode oscillation, and hence oscillation from this source is possible. Therefore, design of a tube within this range of values is considerably less desirable than design of a tube using on within the range of .67 to 1.5.

There is also illustrated in Fig. 6 curves S5, 56 and 57 indicated at dotted lines representing analysis of the transmission line as a series of cascaded T sections for values of 10, 1, and .1, respectively. The curve 55 has a normalized characteristic impedance of 20 at a normalized frequency of 1.02 as is indicated by point 58 and drops rapidly as frequency is increased to a normalized characteristic impedance of 2 at a normalized frequency of 1.12 as is indicated by point 59. Similarly, curves 56 and 57 vary quite rapidly with frequency, and hence good impedance match over a wide range of frequencies to either input or output loads is not possible. Thus, it may be seen that when the input and output coupling devices see the signal wave transmission network substantially as a series of cascaded 1r section filters the impedance to which the external loads must be matched remains constant over a wider range of frequencies than is possible when the coupling device sees T section filters. Since this is accomplished by a coupling structure wherein the coaxial line is connected between adjacent anode members, it may be seen that distinct advantages flow from this structure over the results which can be obtained, for example, by coupling directly to the straps.

Referring now to Fig. 4, there is shown a further modification of this coupling structure wherein the coaxial line is connected to the end anode member and anode member adjacent said end anode member similar to that described in connection with Fig. 1 through 3. However, the end anode member is made narrower in that portion which extends from a region just above the straps back to the support member 11. As a result, the end section of the transmission line more closely resembles a true 11- section.

This completes the description of the particular em bodiments of the invention illustrated herein. However. many modifications thereof will be apparent to persons skilled in the art. For example, the device may be made in arcuate or circular form rather than in the linear form shown. The anode structure is not limited to the particular structure illustrated herein but the principle of design disclosed herein may be applied to various types of anode structure such as helixes, unstrapped anode members, or strapped interdigital anode structures. Furthermore, various structures for forming the electron beam and for directing the electrons along paths adjacent the signal wave transmission network may be used. Accordingly, it is desired that this invention be not limited by the particular details of the embodiments described herein except as defined by the appended claims.

What is claimed is:

1. An electron discharge device comprising a signal wave transmission network having signal input and output means coupled thereto and having a cutoff frequency, said network being capable of sustaining a component of a signal traveling along said network the phase velocity of which at all frequencies passable by said network other than said cutoff frequency is different than the phase velocity of said component at said cutoff frequency, an electron source disposed substantially entirely adjacent one end of said network, and means for directing electrons from said source along paths adjacent said net- Work substantially entirely at velocities which are substantially different from the phase velocity of said component at said cutoff frequency.

2. An electron discharge device comprising a signal wave transmission network'having signal input and output means coupled thereto and having a lower cutoff frequency, said network being capable of sustaining a component of a signal traveling along said network the phase velocity of which at all frequencies passable .by said network other than said cutoff frequency is slower than the phase velocity of said component at said cutoff frequency, an electron source disposed substantially entirely adjacent one end of said network, and means for directing electrons from said source along paths adjacent said network substantially entirely at velocities which are substantially different from the phase velocity of said component at said cutoff frequency.

3. An electron discharge device comprising a signal wave transmission network having signal input and output means coupled thereto and having a cutoff frequency, said network being capable of sustaining a component of a signal traveling along said network the phase velocity of which at all frequencies passable by said network other than said cutoff frequency is different than the phase velocity of said component at said cutoff frequency, an electron source disposed substantially entirely adjacent one end of said network, and means for directing electrons from said source along paths adjacent said network substantially entirely at velocities which are substantially different from the phase velocity of said component at said cutoff frequency comprising means for producing a magnetic field substantially transverse to the direction of motion of said electrons along said paths.

4. An electron discharge device comprising a signal wave transmission network having signal input and output means coupled thereto and having a lower cutoff frequency, said network being capable of sustaining a component of a signal traveling along said network the phase velocity of which at all frequencies passable by said network other than said cutoff frequency is slower than the phase velocity of said component at said cutoff frequency, an electron source disposed substantially entirely adjacent one end of said network, and means for directing electrons from said source along paths adjacent said network substantially entirely at velocities which are substantially different from the phase velocity of said component at said cutoff frequency comprising means for producing a magnetic field substantially transverse to the direction of motion of said electrons along said paths. 7

5. An electron discharge device comprising a signal wave transmission network having signal input and output means coupled thereto and having a cutoff frequency, said network being capable of sustaining a component of a signal traveling along said network the phase velocity of which at all frequencies passable by said network other than said cutoff frequency is different than the phase velocity of said component at said cutoff frequency, an electron source disposed substantially entirely adjacent one end of said network, means for directing electrons from said source along paths adjacent said network substantially entirely at velocities which a're substantially different from the phase velocity of said component at said cutoff frequency comprising means for producing a magnetic field substantially transverse to the direction of motion of said electrons along said paths, and an auxiliary electrode structure having a first portion arranged substantially parallel to said network substantially throughout the length thereof and having portions extending from opposite edges of said first portion toward said network.

6. An electron discharge device comprising a signal wave transmission network having signal input and output means coupled thereto and having a lower cutoff frequency, said network being capable of sustaining a component of a signal traveling along said network the phase velocity of which at all frequencies passable by said network other than said cutoff frequency is slower than the phase velocity of said component at said cutoff frequency, an electron source disposed substantially entirely adjacent one end of said network, means for directing electrons from said source along paths adjacent said network substantially entirely at velocities which are substantially different from the phase velocity of said component at said cutoif frequency comprising means for producing a magnetic field substantially transverse to the direction of motion of said electrons along said paths, and an auxiliary electrode structure having a first portion arranged substantially parallel to said network substantially throughout the length thereof and having portions extending from opposite edges of said first portion toward said network.

References Cited in the file of this patent UNITED STATES PATENTS 2,511,407 Kleen et a1. June 13, 1950 2,673,306 Brown Mar. 23, 1954 2,681,427 Brown et al. June 15, 1954 2,683,238 Millman July 6, 1954 2,808,532 Field Oct. 1, 1957 UNITED STATES PATENT OFFICE CERTIFICATION OF CORRECTION Patent Noi..2,963,62l December 6, 1960 Edward C. Dench It is hereby certified that error appears in the above numbered pat enc requiring correction and that the said Letters Patent should read as corrected below.

' Column 4, line 3, for "conductor 26" read conductor 25 Signed and sealed this 6th day of June 1961.

(SEAL) Attest:

ERNEST W. SWIDER DAVID L. LADD Attesting Officer v Commissioner of Patents 

